UTC TDA2030A LINEAR INTEGRATED CIRCUIT 18W HI-FI AUDIO AMPLIFIER AND 35W DRIVER DESCRIPTION The UTC TDA2030A is a monolithic IC in Pentawatt package intended for use as low frequency class AB amplifier. With Vs=max=44V it is particularly suited for more reliable applications without regulated supply and for 35W driver circuits using low-cost complementary pairs. The UTC TDA2030A provides high output current and has very low harmonic and cross-over distortion. Further the device incorporates a short circuit protection system comprising and arrangement for automatically limiting the dissipated power so as to keep the working point of the output transistors within their safe operating area. A conventional thermal shut-down system is also included.
1
TO-220B
PIN CONFIGURATIONS 1 2 3 4 5
Non inverting input Inverting input -VS Output +VS
ABSOLUTE MAXIMUM RATINGS (Ta=25°C) PARAMETER
SYMBOL
VALUE
UNIT
Supply Voltage Input Voltage Differential Input Voltage Peak Output Current(internally limited) Total Power Dissipation at Tcase=90°C Storage Temperature Junction Temperature
Vs Vi Vdi Io Ptot Tstg Tj
±22 Vs ±15 3.5 20 -40 ~ +150 -40 ~ +150
V V V A W °C °C
ELECTRICAL CHARACTERISTICS (Refer to the test circuit, Vs =±16V,Ta=25°C) PARAMETER
SYMBOL
Supply Voltage Quiescent Drain Current Input Bias Current Input Offset Voltage Input Offset Current
Vs Id
UTC
Ib Vos Ios
TEST CONDITIONS
MIN
TYP
MAX
UNIT
50
±22 80
V mA
0.2 ±2 ±20
2 ±20 ±200
µA mV nA
±6
Vs=±22V
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT PARAMETER Output Power
Power Bandwidth Slew rate Open loop voltage Gain Closed Loop Voltage Gain Total harmonic distortion
Second Order CCIF Intermodulation distortion Third Order CCIF Intermodulation Distortion Input Noise Voltage Input Noise Current Signal to Noise Ratio Input Resistance (pin 1) Supply Voltage Rejection Thermal Shut-Down Junction Temperature
UTC
SYMBOL
TEST CONDITIONS
MIN
TYP
Po
d=0.5%,Gv=26dB,f=40 to 15kHz RL=4Ω RL=8Ω Vs=+-19V, RL=8Ω Po=15W,RL=4Ω
15 10 13
18 12 16 100 8 80
BW SR Gvo
f=1kHz
Gvc d
d2
25.5 Po=0.1 to 14W, RL=4Ω f=40 to 15kHz Po=0.1 to 14W,RL=4Ω f=1kHz Po=0.1 to 9W,RL=8Ω f=40 to 15 kHz Po=4W ,RL=4Ω f2-f1=1 kHz
d3
f1=14 kHz, f2=15kHz
eN
B=curve A B= 22Hz to 22kHz B=curve A B= 22Hz to 22kHz RL=4Ω, Rg=10kΩ, B=curve A Po=15W Po=1W Open loop,f=1kHz
iN S/N
Ri SVR Tj
RL=4Ω,Gv=26dB Rg=22kΩ,f=100Hz
26
UNIT W
KHz V/µ sec dB 26.5
dB
0.08
%
0.03
%
0.5
%
0.03
%
0.08
%
2 3 50 80
0.5
MAX
µV 10 pA 200
106 94 5
dB dB MΩ
54
dB
145
°C
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT TYPICAL APPLICATION +Vs
Vi
C1 1 µF
C5 100nF
C3 100µF D1 1N4001
1 R3 22kΩ
5 UTC TDA2030A
2
4 3
R1 22kΩ
R3 680Ω C2 22 µF
R5
C6 100 µF
C8
R4 1Ω
D1 1N4001
RL
C4 C7 100nF 220nF
-Vs
UTC
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT TEST CIRCUIT +Vs C5 220 µF
C1 1 µF
Vi
C3 100nF D1 1N4001
1 R3 22kΩ
5 UTC TDA2030A
2
4 3
R4 1Ω
R1 13kΩ
R3 680Ω
RL
D1 1N4001
C2 22 µF
C4 C7 100nF 220nF
C6 100 µF
-Vs
+Vs 220 µF
0.1 µF
1N4001
1
22 µF
5 UTC TDA2030A
2
3
100kΩ
C R
4 R4 1Ω
100kΩ 4.7kΩ 2.2 µF
1N4001
C7 220nF
2200 µF
100kΩ
RL=4Ω
Vi
100kΩ 2.2 µF
Fig.1 Single supply amplifier
UTC
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT TYPICAL PERFORMANCE CHARACTERISTICS Fig.3 Output power vs. Supply voltage
140
Gv (dB)
180
Phase 100
90
60
0
Phase
Fig.2 Open loop frequency response Po (W)
24 Gv=26dB d=0.5% f=40 to 15kHz
20
RL=4Ω 16 RL=8Ω
Gain 20
12
-20
8
-60
1 10
2 10
3 10
4 10
5 10
6 10
4
7 10
24
Frequency (Hz)
Fig.4 Total harmonic distortion vs. output power d (%)
d (%)
40
44
Vs (V)
Po (W)
2 10
Vs=32V Po=4W RL=4Ω Gv=26dB
0 10
Vs=38V RL=8Ω f=15kHz
-1 10
36
1 10
Gv=26dB
0 10
32
Fig.5 Two tone CCIF intermodulation distortion
2 10
1 10
28
Order (2f1-f2)
-1 10 Vs=32V RL=4Ω
Order (2f2-f1)
f=1kHz -2 10
-2 10
-1 10
0 10
1 10
Po (W)
2 10
-2 10
1 10
30
Vs=+-15V RL=8Ω
25
3 10
4 10
5 10
Frequency (Hz)
Fig.7 Maximum allowable power dissipation vs. ambient temperture
Fig.6 Large signal frequency response Vo (Vp-p)
2 10
30
Ptot (W)
25
Vs=+-15V RL=4Ω
20
20
15
10
10
5 1 10
UTC
2 10
3 10
Frequency (kHz)
4 10
he a Rt tsin h= k 4° ha C/ vin he W g at Rt sink h= h 8°C avin /W g
ink a ts he te ini g inf vin ha /W ink ats 5°C he ty=2 R
15
5 -50
0
50
100
150
200
Tamb (°C)
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT
UTC TDA2030A
R4 3.3kΩ C4 10 µF
C8 2200 µF
4
3 R5 30kΩ
BD907
R8 1Ω RL=4Ω
C2 22 µF
5
2
R2 56kΩ
BD908
1N4001
1 R3 56kΩ
C5 220 µF /40V
R6 1.5Ω
1N4001
R1 56kΩ
C6 0.22 µF
Vi
C1 2.2 µF
C3 0.22 µF
+Vs
R7 1.5Ω
C7 0.22 µF
Fig. 8 Single supply high power amplifier(UTC TDA2030+BD908/BD907)
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8 PARAMETER Supply Voltage Quiescent Drain Current
Output Power
SYMBOL Vs Id
Po
Voltage Gain Slew Rate Total Harmonic Distortion Input Sensitivity
Gv SR d
Signal to Noise Ratio
S/N
UTC
Vi
TEST CONDITIONS
MIN
Vs=36V d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=39V d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=36V d=0.5%,f=1kHz, RL=4Ω,Vs=39V d=0.5%,RL=4Ω f=1kHz,Vs=36V f=1kHz Po=20W,f=1kHz Po=20W,f=40Hz to 15kHz Gv=20dB,Po=20W, f=1kHz,RL=4Ω RL=4Ω,Rg=10kΩ B=curve A,Po=25W RL=4Ω,Rg=10kΩ B=curve A,Po=25W
TYP
MAX
UNIT
36 50
44
V mA
35 28 W 44 35 19.5
20 8 0.02 0.05 890
20.5
dB V/µsec % % mV
108 100
dB
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT TYPICAL PERFORMANCE CHARACTERISTICS Fig. 10 Output power vs. supply voltage
Fig. 11 Total harmonic distortion vs. output power
Po (W)
d (%) Vs=36V RL=4Ω Gv=20dB
45 0 10 35
25 -1 10 f=15kHz 15 f=1kHz 5 24
28
32
34
36
Vs (V)
40
-2 10
-1 10
Fig. 12 Output power vs. Input level
0 10
1 10
Po (W)
Fig. 13 Power dissipation vs. output power Ptot (W)
Po (W) 20
20
Complete Amplifier
Gv=26dB 15
15
Gv=20dB 10
BD908/ BD907
10
5
UTC TDA2030A
5
0 100
250
UTC
400
550
700
Vi (mV)
0 0
8
16
24
32
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Po (W)
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QW-R107-005,B
UTC TDA2030A LINEAR INTEGRATED CIRCUIT +Vs
Vi
C5 100 µF
C1 1 µF
C3 100nF D1 1N4001
1 R3 22kΩ
5 UTC TDA2030A
2
4 3
C8
R5
R4 1Ω
D2 R1 22kΩ 1N4001
R3 680Ω C2 22 µF
C6 100 µF
RL
C4 C7 100nF 220nF
-Vs Fig. 14 Typical amplifier with split power supply Vs+ C6 100 µF
1
R1 22kΩ
2
5 UTC TDA2030A
3
4 C8
IN
R3 22kΩ
0.22 µF
C1 220 µF
C7 100nF
R8 1Ω
C4 22 µF RL 8Ω
R4 680Ω R7 22kΩ
Vs-
3
4
R5 22kΩ
C9
2
5 UTC TDA2030A
0.22 µF
1 R2 22kΩ
R9 1Ω
C5 22 µF
C2 100 µF
C3 100nF
R6 680Ω
Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V)
UTC
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficulty of precise design due to variable loudspeaker impedance. Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19. The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or low-pass filters. In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100Ω,while that of the Pin (+) is very high, which is also what was wanted. Fig. 18 Power distribution vs. frequency
Fig. 19 Active power filter
100
C1 C2 C3
IEC/DIN NOISE SPECTRUM FOR SPEAKER TESTING
80
Vs+
Morden Music Spectrum
RL
60
R1 R2
R3 3.3kΩ
Vs-
40
100Ω
20
0 1 10
2 10
UTC
3 10
4 10
5 10
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2KΩ,R2=5.6KΩ,R3=33KΩ. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4Ω to 8Ω). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Fig. 20 : 3Way 60W Active Loudspeaker System (Vs=36V)
22kΩ
22kΩ
22kΩ
1N4001
1.5Ω
2
33nF
680Ω
18nF
1
5
BD908
4
UTC TDA2030A
3
2200 µF 1Ω
100 µF
0.22 µF
1N4001
1.5Ω
3.3kΩ
100Ω
BD907
4Ω
1 µF
0.22 µF
IN
0.22 µF
2200 µF
Vs+
Low-pass 300Hz
Woofer Vs+
Band-pass 300Hz to 3kHz
0.22 µF 1N4001
6.8kΩ
3.3nF
2
5
3 1N4001
100 µF
100Ω
Vs+ 0.22 µF 1N4001
100 µF
4
3 1N4001
8Ω
1Ω
2
5 UTC TDA2030A
0.22 µF
1 22kΩ
12kΩ
0.1 µF
22kΩ
100 µF
22kΩ
0.1 µF
Midrange
2.2kΩ
High-pass 3kHz
Vs+
220 µF
4
UTC TDA2030A
8Ω
1
1Ω
22kΩ
18nF
22kΩ
0.22 µF
0.1 µF
3.3kΩ
0.1 µF
47 µF
100Ω
2.2kΩ
UTC
High-pass 3kHz
Tweeter
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT MUSICAL INSTRUMENTS AMPLIFIERS Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms.
TRANSIENT INTER-MODULATION DISTORTION(TIM) Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation(TIM situation.)The best known
Fig.21 High power active box for musical instrument
Fig.22 Overshoot phenomenon in feedback amplifiers
FEEDBACK PATH
20 to 40W Amplifier 汕V4 INPUT V1
PRE AMPLIFIER
V2
V3
POWER AMPLIFIER
OUTPUT V4
20 to 40W Amplifier
V1
20 to 40W Amplifier
V2
20 to 40W Amplifier V3 V4
method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in the other direction the opposite is true.
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT Input Signal
SR(V/µs) m2 m1
Filtered Output Siganal Fig.23 20kHz sawtooth waveform
Fig.24 Inverting sawtooth waveform
The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured, the TIM can be found very simply from:
VOUT
TIM =
* 100
Vsawtooth Fig. 25 TIM distortion Vs. Output Power
Fig. 26 TIM design diagram(fc=30kHz) 2 10
1 10
TIM(%)
UTC2030A BD908/907 Gv=26dB Vs=36V RL=4Ω
RC Filter fc=30kHz
1 10
1% =1 %
=0 . TI M
TI
0 10
M
RC Filter fc=30kHz
TI
-1 10
M =0 .0
1%
0 10
SR(V/米s)
-2 10 -1 10
0 10
1 10
Po(W)
2 10
-1 10 -1 10
0 10
1 10
Vo(Vp-p)
2 10
In Fig.25 The experimental results are shown for the 30W amplifier using the UTC2030A as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an effective way to reduce TIM. The Diagram of Fig.26 originated by SGS can be used to find the Slew-Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM. Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver.
POWER SUPPLY Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage.
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load. The UTC2030(Vsmax=44V) is particularly suitable for substitution of the standard IC power amplifiers(with Vsmax=36V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.27. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater in case than for the case of regulated supplied, with space saving and cost reduction.
Fig.27 DC characteristics of 50W non-regulated supply Ripple (Vp-p)
Vo(V) 36
34 Ripple
4
32
220V Vo
2
3300 µF
30
Vout
0
28
0
Mains(220V) +20% +15% +10% — -10% -15% -20%
UTC
0.4
0.8
1.2
1.6
2.0
Io(A)
Secondary Voltage 28.8V 27.6V 26.4V 24V 21.6V 20.4V 19.2V
DC Output Voltage(Vo) Io=0 43.2V 41.4V 39.6V 36.2V 32.4V 30.6V 28.8V
Io=0.1A 42V 40.3V 38.5V 35V 31.5V 29.8V 28V
Io=1A 37.5V 35.8V 34.2V 31V 27.8V 26V 24.3
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT SHORT CIRCUIT PROTECTION The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground.
THERMAL SHUT-DOWN The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported since the Tj can not be higher than 150°C 2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption.
APPLICATION SUGGESTION The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used. The following table can help the designer.
COMPONENT
RECOMMENDED VALUE
PURPOSE
LARGE THAN RECOMMENDED VALUE
LARGE THAN RECOMMENDED VALUE
R1
22KΩ
Increase of Gain
Decrease of Gain
R2
680Ω
Decrease of Gain
Increase of Gain
R3
22KΩ 1Ω
R5
≈3R2
Increase of input impedance Danger of oscillation at high frequencies with inductive loads. Poor high frequencies attenuation
Decrease of input impedance
R4
Closed loop gaon setting. Closed loop gaon setting. Non inverting input biasing Frequency stacility
C1
1µF
C2
22µF
C3,C4
0.1µF
C5,C6
100µF
C7 C8
0.22µF ≈1/(2π*B*R1)
D1,D2
1N4001
UTC
Upper frequency cutoff Input DC decoupling Inverting DC decoupling Supply voltage bypass Supply voltage bypass Frequency stability Upper frequency cutoff To protect the device against output voltage spikes.
Dange of oscillation Increase of low frequencies cutoff Increase of low frequencies cutoff Dange of oscillation Dange of oscillation
smaller bandwidth
Larger bandwidth Larger bandwidth
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UTC TDA2030A LINEAR INTEGRATED CIRCUIT
UTC assumes no responsibility for equipment failures that result from using products at values that exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or other parameters) listed in products specifications of any and all UTC products described or contained herein. UTC products are not designed for use in life support appliances, devices or systems where malfunction of these products can be reasonably expected to result in personal injury. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner. The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed without notice.
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